The folded dipole is a simple antenna to build. However, it has a acquired something of a complex web of correct and incorrect information surrounding it. The points of these notes is to sort out some of the information, with an emphasis upon what it is correct to say about the folded dipole.

**Fig. 1** shows the essential elements of a folded dipole. It consists of two parallel wires having a constant spacing, S. Each wire has a certain diameter, d1 and d2. The ends of the parallel wires are connected to form a continuous loop. The feedpoint is at the center of the wire having the diameter d1.

We can construct a folded from common materials ranging from house wire to parallel transmission line. With such materials, we can obtain the pattern shown as a free-space azimuth pattern in **Fig. 2**--the same pattern as a single-wire dipole. The folded dipole is a reliable antenna, meaning that we can get it to work without lots of finicky adjustments. Something about the ease of building an antenna seems to go hand-in-hand with not getting a firm grasp on why it works.

In calling the antenna a folded dipole, we should note that the term "dipole" is important to our discussion. "Dipole" is a term that we use as a shorthand for a longer characterization of a single wire antenna. The 1-wire antenna described is a 1/2 wavelength long, resonant, 2-pole antenna. The reference to length is obvious. Being resonant means that the feedpoint impedance will have negligible reactance and hence be purely or close to purely resistive. Having 2 poles means having two transitions from maximum to minimum current--in this case stating at the current maximum located at the center of the antenna.

Now all that we need to deal with is the folded aspect of the antenna. Folding refers not only to the visual appearance of the antenna, but as well to what folding does. Folding a single wire antenna (and thereby doubling the amount of wire needed) creates a combination of an antenna element and an impedance transformer. The same principle has been used with other antenna types. For example, the side-fed rectangle--a good vertically polarized performer for the lower HF bands--has a low feedpoint impedance. Doubling the loop with a crossover at the far end from the feedpoint raises the impedance of the antenna.

Using antenna transformer techniques to raise the impedance of an antenna does not reduce any losses inherent in the antenna operation. Loss resistances will also be transformed. These losses are not significant with the standard horizontal folded dipole, but have been a major misunderstanding of its cousin, the folded monopole.

Relative to a single-wire dipole, the feedpoint impedance will be transformed upward by the ratio R according to the following equation:

where the terms S, d1, and d2 have the meanings shown in **Fig. 1**.

The log of 2S divided by a wire diameter is a complex quantity that hides some of the consequences of the equation. However, consider that if d1 and d2 are equal diameters, then the division of one log by the other log results in a value of 1. Since 1 plus this value is 2 and the square of 2 is 4, then for wires of equal diameter, the impedance transformation ratio is always 4:1 relative to the impedance of a single wire resonant half wavelength dipole.

In free space the impedance, the resonant impedance of a single wire resonant half wavelength antenna that is center-fed is between 71 and 72 Ohms for highly conductive materials like copper. Hence, a folded dipole using equal wire diameters for both wires will be about 284 to 288 Ohms.

Now let's note some other aspects of the equation. There are no rules against using wires of different diameter for d1 and d2. The wire diameter values always occur as divisors (below the division line). Hence, the larger the diameter, the smaller will be the resulting log term. Therefore, we get the following guidelines (remembering that d1 is the diameter of the fed wire):

- 1. If d1<d2, then R is always >4.
- 2. If d1>d2, then R is always <4.

However, R must always be >1. That is, 1 is the limit of R as the ratio of the two log values goes to zero, which would imply an immensely large value for d2 or an infinitesimally small value for d1. The result is that a folded dipole cannot be used to reduce the feedpoint impedance relative to a single-wire dipole.

So far, we have ignored S. Before taking a log for the numerator and for the denominator of the fraction in the equation, we must divide twice the wire spacing by the wire diameter(s). This results in a different value in the numerator and denominator for each different wire spacing we choose. Hence, the impedance transformation ratio will also change with every change of spacing.

There is one exception to this consequence of spacing. If the two log values result in a value of 1 when we divide one by the other, then the result will always be 4, regardless of the spacing. Hence, for the case where both wires have the same diameter, the feedpoint impedance transformation relative to a single-wire dipole will be 4:1 for any reasonable wire spacing.

There is a limit to how far apart we can place the wires and still have a folded dipole. That limit, however, is considerably farther apart than the limit for having an effective transmission line with confined fields. It also can be a tiny spacing--just enough to prevent a short circuit between the wires.

The trick to modeling folded dipoles is to use many segments. The end wires connecting the parallel wires are a limiting factor. In NEC, we want the segment lengths in the parallel wires to be less than a 2:1 ratio in length to the segments in the end wires. In MININEC, we want to use many segments so that the end corners are not mathematically "cut off" in the calculation. So for the models in this exercise, I shall use a frequency of 28.5 MHz with 110 segments along the length of each parallel wire in MININEC to allow a perfectly centered feedpoint. 111 segments is required in NEC. These models will fall well within the calculation constraints of each program type. However, in all cases, the results will apply to bare wire.

As a test case, let's look once more at the question of spacing. We shall use 0.1" diameter copper wires throughout for our initial tests. This diameter is between #12 and #10 AWG wire. I shall present both NEC-2 and MININEC results for comparison. (For reference, the NEC-2 results are from NEC-Win Plus and the MININEC results are from AO 6.5.)

Let's compare the performance of folded dipoles having 3 different spacing values. A 1" spacing corresponds to the use of ladder line of common commercial sorts. A 4.14" spacing corresponds to one recommendation that we use a spacing of 1/100 wavelength. Finally, a spacing of 13.8" corresponds to another recommendation that we use a spacing of 1/30 wavelength. In the table below, length refers to the resonant length of the folded dipole, while gain is the free-space gain in dBi. The feedpoint impedance is given in standard series R +/- jX Ohms terms.

Spacing Length Gain Feedpoint Z inches dBi R +/- jX Ohms 1" Mininec 196.56" 2.10 288.0 + j0.0 NEC-2 196.93" 2.12 286.6 - j0.0 4.14" Mininec 193.70" 2.10 288.0 + j0.0 NEC-2 194.20" 2.12 287.0 - j0.1 13.8" Mininec 186.94" 2.12 287.0 + j0.0 NEC-2 187.40" 2.13 285.8 + j0.0

Note that the two calculating systems yield resonant lengths within about a half inch of each other. As well, the predicted gain is never more than 0.02 dB apart--a truly insignificant amount. Even the resonant resistance values diverge by less than 1.5 Ohms. The systems are certainly consistent with each other.

Nothing in the spacing of the wires of a folded dipoles could produce a difference that would be discernable to the most accurate field measuring equipment available today. There is no aspect of antenna theory that can justify a claim that one spacing value will perform better than another.

Private experience might result in other claims. However, private experience is fraught with many variables of construction and maintenance, as well as antenna location variables. However, equivalently well-constructed folded dipoles of different spacing values will perform equally well when placed in identical antenna settings.

Of course, the actual feedpoint impedance encountered by the builder will vary with the height above ground, just as the feedpoint impedance of a single-wire dipole varies with height. The two curves will show a 4:1 ratio in value, but otherwise be congruent.

Before we leave these folded dipoles, let's note the differences in antenna length. Each antenna was brought to resonance by adjusting its overall length. The wider the spacing, the shorter will be the resonant length. The shortening has two major sources. First, the classic impedance transformation equation does not take into account the end wires. With wide spacing, these wires begin to take up a small part of the antenna length. Second, a 2-wire folded dipole simulates a fat single wire. Just as single-wire dipoles become shorter at resonance with increasing diameter values, so too do folded dipoles with increases in wire spacing.

The handy "468/f" rule of thumb that we use for dipoles is actually only a crude and often inaccurate guide for wire cutting. The resonant length of single-wire and folded dipoles will vary with wire size, spacing (for folded dipoles), and height above ground. If we turn the matter around and cut the antenna according to the old guide, then we can expect different impedance values--including differences in both the resistive and reactive components--as we change wire diameter, spacing, and/or height above ground.

Wire Size Length Gain Feedpoint Z inches dBi R +/- jX Ohms 0.5" Mininec 192.10" 2.10 287.0 + j0.0 NEC-2 193.04" 2.13 285.3 - j0.1 #10 AWG Mininec 194.54" 2.10 288.0 + j0.0 NEC-2 195.09" 2.12 286.9 - j0.0 #12 AWG Mininec 194.90" 2.10 288.0 - j0.0 NEC-2 195.31" 2.12 287.2 - j0.0 #14 AWG Mininec 195.16" 2.10 289.0 + j0.0 NEC-2 195.51" 2.12 287.6 + j0.0 #18 AWG Mininec 195.63" 2.09 290.0 + j0.0 NEC-2 195.88" 2.10 288.5 + j0.0

All values remain within 0.5% of each other for each set of wire sizes between the two calculating systems. More significantly, there is no perceptible difference in performance predicted for the range of wire sizes.

Although there is a change of resonant length as we change wire size, it is considerably less than the length changes required by differences of wire spacing in the folded dipole. The range of spacing in our tests was 13.8:1, while the range of wire sizes was 12.4:1, comparable ranges. However, the length range was only about 1.5" for the wire size differences, but 4.5" for the spacing differences.

With respect to length and performance, a folded dipole acts very much like a single fat wire. In fact, a single wire dipole will have a length of about 199.8" using 0.1" diameter copper wire to be resonant and have a free space gain of about 2.10 dBi. All of our folded dipoles are shorter, since all are effectively much larger in diameter. To have a resonant length equal to that of the #18 AWG wire folded dipole above (about 195.8"), a single copper wire would need to be just about 1" in diameter. (Reminder: all tests are at 28.5 MHz for consistency throughout this exercise.)

At first glance, a folded dipole operates in ways distinctly unlike a transmission line. For example, in a properly functioning transmission line, at any point along the line, the current magnitudes will be equal, but the current phases will be opposite, that is, 180 degrees apart. If a resonant folded dipole acted as a transmission line, we should expect to see the same pattern of current values between the two wires.

To demonstrate this, we can use the model on the lower half of **Fig. 3** to derive the currents along the transmission line. A sample every 20% of the way of a line nearly, but not quite, 1 wavelength long is instructive. We shall present two sets of current phase figures for wire #2: onset derived from the modeling convention of continuously developing the model from left to right, the other from using the dipole junction as the starting point for both wires.

Currents Wire 1 Wire 2 Distance Magnitude Phase Magnitude Phase 0% 1.001 - 0.1 1.001 - 0.0/ 180.0 20% 0.419 18.1 0.419 18.1/-162.0 40% 0.758 173.5 0.758 173.5/- 6.5 60% 0.861 -174.6 0.861 -174.6/ 5.4 80% 0.270 - 31.1 0.270 - 31.0/ 148.8 100% 0.999 - 0.2 0.999 - 0.2/ 179.8

The modeling convention that runs the transmission line wires in opposite directions shows essentially the same values for each point on the line. The convention that starts and ends them in the same direction shows the 180-degree out-of-phase condition.

To illustrate what we actually encounter with a folded dipole, let us turn to the upper portion of **Fig. 3**. The markers represent percentages of distance from the outer end of each wire inward toward the center. If we plot the current magnitudes and phases for a typical folded dipole, we end up with an interesting chart. Let's use our #18 bare copper wire folded dipole with 3" spacing as a test case. Current magnitudes are relative to a maximum value of 1.0, while current phases are relative to a feedpoint value of 0.0 degrees. The first current phase figure for Wire 2 is for continuous modeling so the end 2 of one wire becomes end 1 of the next. The second value presumes a model with both parallel wires starting at the same end of the assembly.

Currents Wire 1 Wire 2 Distance Magnitude Phase Magnitude Phase 0% (end) 0.256 - 74.5 0.244 -106.4/ 73.6 10% 0.463 - 33.8 0.432 -153.0/ 27.0 20% 0.682 - 20.2 0.659 -166.5/ 13.5 30% 0.855 - 12.4 0.842 -172.6/ 7.4 40% 0.964 - 6.2 0.960 -176.1/ 3.9 50% 1.000 0.0 1.000 -177.9/ 2.1

The chart ends at the antenna center point because the opposite side of the antenna shows virtually identical current values at the prescribed points. Although the current magnitudes are comparable (and would be closer had the wire been without any loss at all), the current phase values show a curious pattern. Corresponding points along the wires show similar absolute current phase values, but they are opposite in sign when both wires are modeled from the same point (e.g., left to right). The pattern is distinctly unlike a transmission line that is acting like a transmission line, even with the far end a short circuit.

A phase pattern similar to the one shown is necessary if the folded dipole is to radiate. Radiation is simply the ability of the fields that result from the current levels at each point along the antenna to expand without limit. This condition is unlike that in a transmission line, where the fields are confined such that radiation is negligible. For that condition to exist, the current magnitudes would have to be equal, and the phase values must be exactly opposite. So we have a mystery: how can we make sense out of the current magnitudes and phases along a folded dipole?

The pattern of current magnitudes and phase angle hides a small tale, one about the fact that a folded dipole has two sets of currents. It is the combination of these two current sets that results in the readings. One set is the radiation currents (Ir), which should be (if the tale is correct) quite similar to those on a standard dipole. The other set is comprised of what some call "transmission line" currents (It). From the modeled current readings, we can separate the two sets. All we need to do is take half the sum of the currents at corresponding points along the folded dipole and we get the value of Ir. If we take half the difference of the currents on each wire, we arrive at It. Kuecken pointed this out in his book *Antennas and Transmission lines*.

The following table provides the modeled values for a bare-wire folded dipole resonant at 28.0 MHz. The values given are for the fed wire (Wire 1), the "other wire" (Wire 2), It (transmission line current), Ir (radiation current), and the corresponding current value for a single wire resonant dipole at the same relative distance from the end. The sampled positions are 10, 30, 50, and 80 percent of the distance from one end of the antenna toward the feedpoint in the center. For each entry, the format is current magnitude/phase angle, where the magnitude is relative to a feedpoint current of 1.0, and the phase angle is in degrees relative to a feedpoint phase angle of 0.0 degrees

Folded Dipole Currents (with Dipole Currents for Comparison) Folded Dipole Standard Dipole Position Wire 1 Wire 2 It Ir I 10 0.3740/-59.38 0.3449/+57.79 0.3069/-89.38 0.1878/-4.59 0.1748/-4.44 30 0.5809/-32.42 0.5437/+27.04 0.2973/-89.38 0.4884/-3.77 0.4771/-3.86 50 0.7769/-19.77 0.7506/+14.68 0.4530/-89.93 0.7295/-2.85 0.7228/-3.06 80 0.9649/- 7.61 0.9584/+ 5.63 0.1109/-89.30 0.9552/-1.01 0.9541/-1.60

There is a very good correlation between the folded-dipole radiation currents as derived by the simple summing method and the single-wire dipole currents at the corresponding points along the antenna length. The correlation cannot be perfect, because the simple summing method does not take into account the currents on the end wires of the folded dipole. They are short, but significant. The current magnitude and phase angle both undergo part of their continuing change in those wires. Nevertheless, the differences between the folded-dipole radiation currents and the corresponding currents on a single-wire dipole are small enough that we should expect to discover any difference in the radiation strength or pattern between the two antennas. And, of course, we do not.

Ideally, the transmission line currents should all show a phase angle of -90 degrees. The very slight offset is due both to the end wire phase angle changes and to the resistance of the copper wire used in the test model (composed of AWG #18 wire with a diameter of 0.0403" along with a wire spacing of 1"). Also ideally, the magnitudes should be the same at each point, but are not for similar reasons.

The key element in the transmission line currents is their relative phase angle--almost perfectly -90 degrees out of phase with the source current. Hence, the transmission line currents represent stored energy rather than expended energy, except for the minute offset from a perfect -90 degrees. As a result, the radiation currents consume all of the RF energy supplied to the antenna in the form of its transformation into indefinitely large expanding electromagnetic fields. Despite energy storage, there is none left over at the end of a transmission.

The existence of transmission line currents within a folded dipole has resulted in a number of erroneous practices based on the use of transmission lines as transmission lines. For example, some folks have proposed that we short the folded dipole at a position equal to a quarter wavelength from the feedpoint outward times the velocity factor of the parallel line used to form the folded dipole. This practice remains to be modeled in NEC-4, which permits the modeler to provide each wire with an insulating sheath with a specified conductivity and dielectric constant.

The first step in considering antennas made from insulated wire is to consider the normal range of velocity factors that apply to antennas (in contrast to those that apply to transmission lines). I began with a 28-MHz dipole that was 204" long and fed in the center of the bare AWG #14 (0.0641" diameter) wire. Then I modeled an identical antenna, but added an insulated sheath with a dielectric constant of 2.5 (about in the middle of the plastics materials range used for wire) and a conductivity of 1e-10 Ohms/meter (a very good insulator). I made the insulation about .047" thick--a goodly insulation. Then I re-resonated the dipole at a length of 195.66". This yielded a velocity factor for the insulated wire of 0.959, a typical value for heavily insulated wire. Thinner insulation would have yielded higher values--or longer resonant dipoles. This little exercise gives us something against which to compare a folded dipole composed of insulated wire.

I went through the same exercise with the folded dipole which we examined in its bareness: 2 AWG #18 wires separated by an inch center-to-center. The original folded dipole was 198" long at resonance. Then I covered the wires with insulation that was also 0.47" thick and re-resonated the assembly. The new folded dipole was 191.5" long, for a velocity factor of 0.968, slightly higher than our single wire dipole. In both cases--the single-wire and the folded dipoles, the feedpoint impedance decreased due to the shortening of the wires. The single wire dipole went from 72.8 Ohms bare to 67.7 Ohm thickly covered. The folded dipole dropped from 289.2 Ohms bare to 274.1 Ohms thickly covered.

I next took down the current readings on both wires so that I could calculate the radiation currents (Ir) and the transmission line currents (It) to see if they corresponded to those in the bare wire folded dipole. The calculations yielded the following table.

Insulated Folded Dipole Currents (with Dipole Currents for Comparison) Folded Dipole Standard Dipole Position Wire 1 Wire 2 It Ir I 10 0.3914/-60.83 0.3531/+57.53 0.3198/-89.89 0.1914/-6.57 0.1748/-4.44 30 0.5946/-34.45 0.5435/+25.88 0.2868/-89.87 0.4922/-5.77 0.4771/-3.86 50 0.7845/-21.40 0.7468/+12.52 0.2241/-89.82 0.7324/-4.87 0.7228/-3.06 80 0.9656/- 8.32 0.9546/+ 2.28 0.0889/-89.49 0.9560/-3.05 0.9541/-1.60

Nothing in the new table distinguishes the currents in the insulated folded dipole from those of the bare wire version, with the possible exception of a nearly uniform 2-degree displacement of the radiation currents. Allowing for the fact that the technique of calculation is approximate--due to reason noted earlier--nothing in the table suggests that we should treat an insulated folded dipole any differently from a bare-wire folded dipole once each is brought to resonance. In fact, both the bare and insulated versions of the antenna show the same gain.

Indeed, the current progression in the insulated wires shows only a single set of curves each side of the feedpoint position, just like the progression in the bare wire version. The upshot is that we need not treat a resonant folded dipole made of insulated parallel transmission line like a transmission line. We can ignore the "transmission line" velocity factor and simply adjust the overall antenna length according to the antenna velocity factor created by the line insulation. The practice of shorting out a folded dipole at the point indicated by the transmission line velocity factor has never shown any evidence of doing anything but shorting out the wires at that point. Finding the resonant length of the folded dipole will be challenge enough.

The impedance transformation possibilities, however, should not be overlooked. The rules of thumb for transformation ratios that are more than or less than 4:1 can be useful in some contexts. Before looking at potential applications, let's first look briefly at the levels of departure from 4:1 as we systematically vary the element diameters. We shall use the 3" spacing from earlier samples, but this time, we shall run each wire through a range of 0.1 to 0.5 inches in diameter--with one wire increasing as the other decreases.

To perform the modeling for this task, we shall set aside NEC-2. NEC has a known difficulty in dealing with closely spaced wires of different diameters. Fortunately, MININEC has no such limitation and handles the calculation task with ease. We shall list the impedance ratio calculated by the equation, the resultant feedpoint impedance, and then the modeled values. This should give us a quick view as to whether the calculations and models reliably coincide.

--------- Calculated --------------- --------- Modeled ---------------- Diameter Diameter Z Ratio Feed Z Length Gain Feed Impedance d1 d2 R=Z Ohms inches dBi R +/- jX Ohms 0.1 0.5 7.01 498 193.34 2.09 493.0 + j0.0 0.2 0.4 5.09 361 193.20 2.10 363.0 + j0.0 0.3 0.3 4.00 284 193.10 2.10 288.0 - j0.0 0.4 0.2 3.23 229 193.48 2.11 234.0 - j0.0 0.5 0.1 2.58 183 193.96 2.11 189.0 - j0.0

Given that the calculations do not account for the end wires, the coincidence of models and calculations is excellent. Incidentally, in all models, the end wires were sized to match the smaller of the two diameters involved. Moreover, the absence of any perceptible change of gain in the series of models is notable. However we size the wires in our folded dipole, it gives us dipole performance. To at least some degree, this convention accounts for the very small differences in resonant lengths of the models.

In many beams using the dipole as a driven element, the feedpoint impedance will be far less than 70-72 Ohms. Values from 10 to 50 Ohms are common, although values above 20-25 Ohms are preferred in order to reduce power losses from the accumulation of small resistances at connections. Using a folded dipole with "designer" values for element diameters and spacing, it is possible to raise the impedance to match almost any value higher than the initial feedpoint impedance. One option is to use a low transformation ratio to arrive directly at 50 Ohms. A second option is to use a higher value to arrive at 200 Ohms and then to use a 4:1 balun at the feedpoint to return to 50 Ohms with an accompanying reduction on possible common mode currents on the coax. Although HF use of folded dipole drivers is rare, at VHF they are still very popular.

Frequency Max. Gain Feed Impedance Pattern MHz dBi R +/- jX Ohms No. of lobes 3.5 2.12 287 - j 1 2 7.0 2.27 5 - j 160 2 10.1 3.31 540 - j 750 6 14.0 3.34 25 - j 330 4 18.1 4.71 480 + j 15 10 21.0 4.26 85 - j 530 6 24.9 4.75 550 - j 310 14 28.0 5.03 225 - j 750 8

The gain figures and the number of pattern lobes coincide with numbers we would obtain from a single-wire dipole pressed into multi-band doublet service. What differs is the impedance value set. The difficulty of using a folded dipole on an even harmonic of the band for which it is initially resonated lies in the very low resistive component of the feedpoint impedance. By the sixth harmonic, we have a value that, while low, is well within the capabilities of most ATUs. In contrast, the second harmonic impedance of 5 Ohms is likely beyond the reach--or at least the efficient range--of most ATUs. The 4th harmonic (20 meters in this sample) might well be matchable, depending upon ATU design.

**Fig. 4** shows the free-space azimuth pattern for 14 MHz, with its typical 2 wavelength 4-lobe pattern. **Fig. 5** presents the 6-lobe, 3 wavelength pattern for 21 MHz. The point of these figures shows up in **Fig. 6**, the pattern for 18.1 MHz. At about 2.5 wavelengths long, the antenna shows both the growing lobes for the 3 wavelength pattern and the diminishing lobes for the 2 wavelength pattern--for a total of 10 lobes.

Using a folded dipole as a multi-band doublet--with parallel feedline to an antenna tuner--thus becomes a matter of matching rather than of pattern development. Very low impedances may also be lossy, thus reducing performance even if a match can be obtained from a given ATU and feedline length.

For multi-band use, a folded dipole offers no advantage over a single-wire doublet of the same approximate length. Indeed, in the final analysis, perhaps the only reason for using a folded dipole is where the impedance transformation is of special interest, that is, where it may resolve an antenna design challenge. A secondary use would be to offer a path to discharge static charge build-up and thus to reduce one (of the many) noise sources. However, there are other means to this same goal.

Otherwise, the folded dipole performs just like a fat single-wire dipole.

There are also two interesting variations of the folded dipole, as suggested in **Fig. 7**. We may call them the end-gapped version and the center-short version.

The end-gapped version of the folded dipole simply omits the end wire, but only one end-wire. A folded dipole is actually two linear dipoles in close proximity--close enough that the wires show transmission-line as well as radiation currents. The dipoles meet at high-voltage, low-current points as each end. We may open one of the high-voltage region contacts with very little effect on the basic antenna properties, that is, on the radiation pattern and the feedpoint impedance. We might have to readjust the total length of the antenna if a resonant feedpoint impedance is important to a given antenna installation. But we would not change the performance as a radiating element.

The version of the folded dipole with the center short from one long wire to the other has a special application. Suppose that we feed the antenna (very slightly off-center, of course) with a transmission line for which one conductor forms a common or ground lead. We might connect the common lead to the short and the other lead to the long wire. In the process, we do not change the essential performance properties of the folded dipole. However, we do obtain a means of connecting the structure to the support mast in the VHF and UHF ranges. That configuration reduces the likelihood that surges from electrical storms will be conveyed to the equipment.

Although I have run both types of folded-dipole variants through numerous models at VHF, let's set them up using our 10-meter model. The standard version uses two AWG #18 wires spaced 1" apart. With a total length of 198", the model uses 199 segments per long wire. The model of the end-gapped folded dipole simple omits one of the 1-segment end wires, but is otherwise identical to the standard model. The center-short version requires a small set of changes. The long wires each become two wires that meet at the center. Each of these wires has 99 segments. I added a new wire from one center junction to the other. I then placed the feedpoint or source on the first segment of the wire extending from the short to the end. If my descriptions have been correct, we should expect virtually identical performance from the three folded-dipole variations.

Modeled performance of 3 folded-dipole variations in a free-space environment Version Gain Feedpoint Impedance dBi R +/- jX Ohms Standard 2.10 289.1 + j 2.6 End-Gapped 2.09 287.8 + j 1.4 Center-Shorted 2.10 288.0 + j 9.3

The only way to tell the antennas apart--besides the obvious visible differences--is to perform a current-sorting exercise on the 3 versions. I did this for some VHF folded dipoles. **Fig. 8** shows the radiation currents along the standard and the end-gapped version of 2-meter folded dipoles. Because the center-short version has connections at both ends, the currents do not drop as close to zero in the end segments as they do with one end of the end-gap version. (Of course, NEC current reports never go quite to zero in a linear wire end segment because the effective position for the current is at the center of the last segment, not its outer end.) Therefore, the center-short and the standard versions of folded dipole have the same radiation-current curves (within limits that are too small to show up in these kinds of graphs).

Where the currents for the 3 antennas show significant variation is in the pattern of transmission line currents. Essentially, for all three versions of the folded dipole, the current phase is 90 degrees from the phase of the current at the source or feedpoint. However, the transmission-line current magnitude for the standard folded dipole shows a symmetrical pattern with its minimum at the long-wire center and maximum values at the long-wire ends. **Fig. 9** shows this pattern for the standard folded dipole, using a VHF model. Interestingly, both the end-gapped version and the center-short versions show virtually identical patterns that vary from the standard version. From the feedpoint toward the open end of the end-gap version or from the shorting bar away from the feedpoint, the transmission-line currents decrease from their feedpoint region value toward zero. At the same time, the current magnitude distribution on the feedpoint side toward the closed end (to the right on the graph) result in higher current magnitudes--in fact about as much higher than the standard version as the low end is lower than the standard version. However, at the center of the antenna, the transmission-line currents have very comparable values.

The differences in transmission-line current distribution between standard and variant versions would make a difference only if we end-feed the folded dipole, as in the many variations on the J-pole, and then only in the impedance at the end feedpoint. However, the center-short version of the antenna is normally fed at the center or as close to it as may be feasible. Hence, we would not be able on range tests to tell the difference between the center-short version and a standard version. Equally, the construction difference used for the end-gap version would hide itself in range test, which would show only the radiation patterns and field strengths for any tested version.

You might note that these notes on the folded dipole do not have a section entitled "conclusion." As well, you may also note the multiple updates to these notes. Each time that I think these notes should end, I learn something new and interesting (at least to me) about folded dipole behavior. I have no good reason to think that my latest additions and revisions should be any different.

*Updated 03-12-2000, 12-04-2001, 09-24-2004, 10-02-2006. © L. B. Cebik, W4RNL. Data may be used for personal purposes, but may not be reproduced for publication in print or any other medium without permission of the author.*